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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
features
D Compact Converter Solution in UltraSmall D
10-Pin MSOP With Only Four External Capacitors Required Evaluation Module Available (TPS60210EVM-167)
D Regulated 3.3-V Output Voltage From a D D D D D D
*
1.8-V to 3.6-V Input Voltage Range UltraLow Operating Current in Snooze Mode, Typical 2 A With up to 2-mA Output Current Less Than 5-mV(PP) Output Voltage Ripple Achieved With Push-Pull Topology Integrated Low-Battery and Power-Good Detector Switching Frequency Can Be Synchronized to External Clock Signal Extends Battery Usage With up to 90% Efficiency and 35-A Quiescent Current Easy-To-Design, Low Cost, Low EMI Power Supply Since No Inductors Are Used
applications
D Replaces DC/DC Converters With Inductors
in Battery-Powered Applications Like: - Two Battery Cells to 3.3-V Conversion - MSP430 Ultralow-Power Microcontroller and Other Battery Powered Microprocessor Systems - Glucose Meters and Other Medical Instruments - MP3 Portable Audio Players - Backup-Battery Boost Converters - Cordless Phones, PDAs
description
The TPS6021x step-up, regulated charge pumps generate a 3.3-V 4% output voltage from a 1.8-V to 3.6-V input voltage. These devices are typically powered by two alkaline, NiCd, or NiMH battery cells or by one primary lithium MnO2 (or similar) coin cell and operate down to a minimum supply voltage of 1.6 V. Continuous output current is a minimum of 100 mA for the TPS60210 and TPS60211, and 50 mA for the TPS60212 and TPS60213, all from a 2-V input.
TPS60210 PEAK OUTPUT CURRENT vs INPUT VOLTAGE
350 300 250
INPUT 1.6 V to 3.6 V Ci 2.2 F R1
TPS60210 7 IN OUT 5 R3 LBI LBO 4 C1 1 F 3 9 ON/OFF 10
OUTPUT 3.3 V Co 2.2 F Low Battery Warning
1 R2
C1+ C1- SNOOZE GND 2
C2+ C2-
6 8 C2 1 F
IO - Output Current - mA
200 150 100 50 0 1.6
Figure 1. Typical Application Circuit With Low-Battery Warning
2.0
2.4
2.8
3.2
3.6
VI - Input Voltage - V Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
Copyright (c) 2000, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
description (continued)
Three operating modes can be programmed using the SNOOZE pin. When SNOOZE is low, the device is put into snooze mode. In snooze mode, the device operates with a typical quiescent current of 2 A while the output voltage is maintained at 3.3 V 6%. This is lower than the self-discharge current of most batteries. Load current in snooze mode is limited to 2 mA. When SNOOZE is high, the device is put into normal operating mode. During normal operating mode, the device operates in the newly developed linskip mode where it switches seamlessly from the power saving pulse-skip mode at light loads to the low-noise constant-frequency linear-regulation mode once the output current exceeds the linskip current threshold of about 7 mA. In this mode, the device operates from the internal oscillator. The device is synchronized to an external clock signal if SNOOZE is clocked; thus switching harmonics can be controlled and minimized. Only four external capacitors are needed to build a complete low-ripple dc/dc converter. The push-pull operating mode of two single-ended charge pumps assures the low output voltage ripple as charge is continuously transferred to the output. All the devices can start with full load current. The devices include a low-battery detector that issues a warning if the battery voltage drops below a user-defined threshold voltage or a power-good detector that goes active when the output voltage reaches about 90% of its nominal value. This dc/dc converter requires no inductors; therefore, EMI of the system is reduced to a minimum, making it easier to use in designs. It is available in the small 10-pin MSOP package (DGS).
DGS PACKAGES TPS60210 TPS60212 TPS60211 TPS60213
LBI GND C1- C1+ OUT
1 2 3 4 5
10 9 8 7 6
LBO SNOOZE C2- IN C2+
GND GND C1- C1+ OUT
1 2 3 4 5
10 9 8 7 6
PG SNOOZE C2- IN C2+
AVAILABLE OPTIONS TA PART NUMBER TPS60210DGS - 40C to 85C TPS60211DGS TPS60212DGS TPS60213DGS MARKING DGS PACKAGE AFD AFE AFF AFG OUTPUT CURRENT (mA) 100 100 50 50 OUTPUT VOLTAGE (V) 3.3 3.3 3.3 3.3 DEVICE FEATURES Low-battery detector Power-good detector Low-battery detector Power-good detector
The DGS package is available taped and reeled. Add R suffix to device type (e.g., TPS60210DGSR) to order quantities of 3000 devices per reel.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
functional block diagrams
TPS60210 and TPS60212 with low-battery detector
0 Oscillator 180
Charge Pump 1
IN C1+ C1- C1
SNOOZE Control Circuit _ + VREF Shutdown/ Start-Up Control + - OUT Charge Pump 2 C2+ C2- C2
_ + + - 0.8 x VIN
_ + VREF + -
LBI
GND
LBO
TPS60211 and TPS60213 with power-good detector
0 Oscillator 180
Charge Pump 1
IN C1+ C1- C1
SNOOZE Control Circuit _ + VREF Shutdown/ Start-Up Control + - OUT Charge Pump 2 C2+ C2- C2
_ + + - 0.8 x VIN
_ + VREF + -
GND
PG
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
Terminal Functions
TERMINAL NAME C1+ C1- C2+ C2- GND IN LBI/GND NO. 4 3 6 8 2 7 1 I I I/O Positive terminal of the flying capacitor C1 Negative terminal of the flying capacitor C1 Positive terminal of the flying capacitor C2 Negative terminal of the flying capacitor C2 Ground Supply input. Bypass IN to GND with a capacitor of a minimum of 2.2 F. Low-battery detector input for TPS60210 and TPS60212. A low-battery warning is generated at the LBO pin when the voltage on LBI drops below the threshold of 1.18 V. Connect LBI to GND or VBAT if the low-battery detector function is not used. For the devices TPS60211 and TPS60213, this pin is a ground (GND pin). Open-drain low-battery detector output for TPS60210 and TPS60212. This pin is pulled low if the voltage on LBI drops below the threshold of 1.18 V. A pullup resistor should be connected between LBO and OUT or any other logic supply rail that is lower than 3.6 V. Open-drain power-good detector output for TPS60211 and TPS60213. As soon as the voltage on OUT reaches about 90% of its nominal value, this pin goes active high. A pullup resistor should be connected between PG and OUT or any other logic supply rail that is lower than 3.6 V. Regulated 3.3-V power output. Bypass OUT to GND with the output filter capacitor Co. Three operating modes can be programmed with the SNOOZE pin. - SNOOZE = Low programs the device in the snooze mode, enabling ultralow operating current while still maintaining the output voltage to within 3.3 V 6%. - SNOOZE = High programs the device into normal operation mode where it runs from the internal oscillator. - If an external clock signal is applied to the SNOOZE pin, the charge pump operates synchronized to the frequency of the external clock signal. DESCRIPTION
LBO/PG
10
O
OUT
5
O
SNOOZE
9
I
detailed description
operating principle The TPS6021x charge pumps provide a regulated 3.3-V output from a 1.6-V to 3.6-V input. They deliver a minimum 100-mA load current while maintaining the output at 3.3 V 4%. Designed specifically for space critical battery-powered applications, the complete converter requires only four external capacitors. The device is using the push-pull topology to achieve the lowest output voltage ripple. The converter is also optimized for a very small board space. It makes use of small-sized capacitors, with the highest output current rating per output capacitance. The TPS6021x circuits consist of an oscillator, a voltage reference, an internal resistive feedback circuit, an error amplifier, two charge-pump power stages with high-current MOSFET switches, a shutdown/start-up circuit, and a control circuit (see functional block diagrams). push-pull operating mode The two single-ended charge-pump power stages operate in the push-pull operating mode (i.e., they operate with a 180C phase shift). Each single-ended charge pump transfers a charge into its flying capacitor (C1 or C2) in one-half of the period. During the other half of the period (transfer phase), the flying capacitor is placed in series with the input to transfer its charge to the load and output capacitor (Co). While one single-ended charge pump is in the charge phase, the other one is in the transfer phase. This operation ensures that there is a continuous flow of charge to the load, hence the output capacitor no longer needs to buffer the load current for half of the switching cycle, avoiding the high, inherent output voltage ripple of conventional charge pumps. In order to provide a regulated output voltage of 3.3 V, the TPS6021x devices operate either in constant-frequency linear-regulation control mode or in pulse-skip mode. The mode is automatically selected based on the output current. If the load current is low, the controller switches into the power-saving pulse-skip mode to boost efficiency at low output power.
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SLVS296 - JUNE 2000
detailed description (continued)
constant-frequency mode When the output current is higher than the linskip current threshold, the charge pump runs continuously at the switching frequency fOSC. The control circuit, fed from the error amplifier, controls the charge on C1 and C2 by regulating the rDS(on) of the integrated MOSFET switches. When the output voltage decreases, the rDS(on) decreases as well, resulting in a larger voltage across the flying capacitors C1 and C2. This regulation scheme minimizes output ripple. Since the device switches continuously, the output ripple contains well-defined frequency components, and the circuit requires smaller external capacitors for a given output ripple. However, constant-frequency mode, due to higher operating current, is less efficient at light loads. For this reason, the device switches seamlessly into the pulse-skip mode when the output current drops below the linskip current threshold. pulse-skip mode The device enters the pulse-skip mode when the load current drops below the linskip current threshold of about 7 mA. In pulse-skip mode, the controller disables switching of the power stages when it detects an output voltage higher than 3.3 V. It skips switching cycles until the output voltage drops below 3.3 V. Then the controller reactivates the oscillator and switching of the power stages starts again. A 30-mV output voltage offset is introduced in this mode. The pulse-skip regulation mode minimizes operating current because it does not switch continuously and deactivates all functions except the voltage reference and error amplifier when the output is higher than 3.3 V. Even in pulse-skip mode the rDS(ON) of the MOSFETs is controlled. This way the energy per switching cycle that is transferred by the charge pump from the input to the output is limited to the minimum that is necessary to sustain a regulated output voltage, with the benefit that the output ripple is kept to a minimum. When switching is disabled in pulse-skip mode, the load is isolated from the input. start up, snooze mode, short circuit protection During start-up (i.e., when voltage is applied to the supply pin IN) the input is connected to the output until the output voltage reaches 0.8 x VI. When the start-up comparator detects this limit, the actual charge pump output stages are activated to boost the voltage higher than the input voltage. This precharging of the output current with a limited current ensures a short start-up time and avoids high inrush currents into an empty output capacitor. Driving SNOOZE low, programs the device into the snooze mode. In this mode, the converter will still maintain the output voltage at 3.3 V 6%. The operating current in snooze mode, is however, drastically reduced to a typical value of 2 A, while the output current is limited to a maximum of 2 mA. If the load current increases above 2 mA, the controller recognizes a further drop of the output voltage and the device enters the start-up mode to bring the voltage up to its nominal value again. However, it does not switch into the normal operating mode. The device limits short circuit currents to typically 60 mA. synchronization to an external clock signal The operating frequency of the charge pump is limited to 400 kHz in order to avoid troublesome interference problems in the sensitive 455-kHz IF band. The device can either run from the integrated oscillator, or an external clock signal can be used to drive the charge pump. The maximum frequency of the external clock signal is 800 kHz. The switching frequency used internally to drive the charge pump power stages is half of the external clock frequency. The external clock signal is applied to the SNOOZE-pin. The device will switch into the snooze mode if the signal on SNOOZE is held low for more than 10 s. When the load current drops below the linskip current threshold, the device enters the pulse-skip mode but stays synchronized to the external clock signal.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
detailed description (continued)
low-battery detector (TPS60210 and TPS60212) The low-battery comparator trips at 1.18 V 5% when the voltage on pin LBI ramps down. The voltage V(TRIP) at which the low-battery warning is issued can be adjusted with a resistive divider as shown in Figure 2. The sum of resistors R1 and R2 is recommended to be in the 100-k to 1-M range. LBO is an open drain output. An external pullup resistor to OUT, or any other voltage rail in the appropriate range, in the 100-k to 1-M range is recommended. During start-up, the LBO output signal is invalid for the first 500 s. LBO is high impedance when the device is programmed into snooze mode. If the low battery function is not used, connect LBI to ground and leave LBO unconnected. When the device is programmed into snooze mode (SNOOZE = LOW), the low-battery detector is disabled.
VO IN R3 R1 LBO _ + VREF + - LBI R2 VBAT
V (TRIP) + 1.18 V 1 ) R1 R2
Figure 2. Programming of the Low-Battery Comparator Trip Voltage A 100-nF ceramic capacitor should be connected in parallel to R2 if large line transients are expected. These voltage drops may inadvertently trigger the low-battery comparator and produce a wrong low-battery warning signal at the LBO pin. Formulas to calculate the resistive divider for low-battery detection, with VLBI = 1.13 V to 1.23 V and the sum of resistors R1 and R2 equal 1 M: R2 + 1 MW V V LBI (1) (2)
Bat R1 + 1 MW * R2 Formulas to calculate the minimum and maximum battery voltage: R1 V Bat(min) +V LBI(min) (min) R2 ) R2 (max)
(3)
(max) ) R2 (min) (min)
R1 V Bat(max) +V LBI(max)
(max) R2
(4)
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SLVS296 - JUNE 2000
detailed description (continued)
Table 1. Recommended Values for the Resistive Divider From the E96 Series (1%)
VIN/V 1.6 1.7 1.8 1.9 2.0 R1/k 267 301 340 374 402 R2/k 750 681 649 619 576 VTRIP(MIN)/V 1.524 1.620 1.710 1.799 1.903 VTRIP(MAX)/V 1.677 1.785 1.887 1.988 2.106
power-good detector (TPS60211 and TPS60213) The power-good output is an open-drain output that pulls low when the output is out of regulation. When the output rises above 91% of its nominal voltage, the power-good output is released. When the device is programmed into snooze mode (SNOOZE = LOW), the power-good detector is disabled and PG is high impedance. In normal operation, an external pullup resistor must be connected between PG and OUT, or any other voltage rail in the appropriate range. The pullup resistor should be in the 100-k to 1-M range. If the PG output is not used, it should remain unconnected.
absolute maximum ratings over operating free-air temperature range (unless otherwise noted)
Voltage range: IN, OUT, SNOOZE, LBI, LBO, PG to GND . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 V to 3.6 V C1+, C2+ to GND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 V to (VO + 0.3 V) C1-, C2- to GND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 V to (VI + 0.3 V) Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Dissipation Rating Table Continuous output current: TPS60210, TPS60211 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150 mA TPS60212, TPS60213 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 75 mA Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -55C to 150C Maximum junction temperature, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 150C
Stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating conditions" is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE 1 FREE-AIR TEMPERATURE PACKAGE DGS TA 25C POWER RATING 424 mW DERATING FACTOR ABOVE TA = 25C 3.4 mW/_C TA = 70C POWER RATING 178 mW TA = 85C POWER RATING 136 mW
The thermal resistance junction to ambient of the DGS package is RTH-JA = 294C/W.
recommended operating conditions
MIN Input voltage range, VI Input capacitor, Ci Flying capacitors, C1, C2 Output capacitor, Co Operating junction temperature, TJ -40 1.6 2.2 1 2.2 125 NOM MAX 3.6 UNIT V F F F C
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
electrical characteristics at Ci= 2.2 F, C1 = C2 = 1 F, Co = 2.2 F, TA = -40C to 85C, VI = 2.4 V, SNOOZE = VI (unless otherwise noted)
PARAMETER IO(MAX) Maximum continuous output current TEST CONDITIONS TPS60210 and TPS60211, VI = 2 V TPS60212 and TPS60213, VI = 2 V 1.6 V < VI < 1.8 V, 0 < IO < 0.25 x IO(MAX) Output voltage VO Output voltage in snooze mode VPP I(Q) f(OSC) f(SYNC) VIL VIH Ilkg Output voltage ripple Quiescent current (no-load input current) Quiescent current in snooze mode Internal switching frequency External clock signal frequency External clock signal duty cycle SNOOZE input low voltage SNOOZE input high voltage SNOOZE input leakage current LinSkip current threshold VI = 1.6 V to 3.6 V VI = 1.6 V to 3.6 V SNOOZE = GND or VI VI = 2 V to 3 V VI = 2.4 V, TC = 25C VI = 2.4 V, TC = 25C 2 V < VI < 3.3 V, TA = 25C VI = 2.4 V, 1 mA < IO < IO(MAX), 10 mA < IO < IO(MAX), IO = 0.5 x IO(MAX), VO = 0 V 1.8 V < VI < 2 V, 2 V < VI < 3.3 V, 3.3 V < VI < 3.6 V, SNOOZE = GND, IO < 2 mA IO = IO(MAX) 0 < IO < 0.5 x IO(MAX) 0 < IO < IO(MAX) 0 < IO < IO(MAX) 1.8 V < VI < 3.6 V, MIN 100 50 3 3.17 3.17 3.17 3.1 3.3 3.3 3.3 3.3 5 35 2 200 400 30% 0.7 x VI 0.01 7 0.015 %/mA 0.008 0.28 60 %V mA 0.1 300 600 70 5 400 800 70% 0.3 x VI V V A mA 3.43 3.43 3.47 3.47 TYP MAX UNIT mA mA V V V V V mVPP A A kHz kHz
IO = 0 mA, VI = 1.8 V to 3.6 V SNOOZE = GND, IO = 0 mA
Output load regulation
Output line regulation I(SC) Short circuit current
electrical characteristics for low-battery comparator of devices TPS60210 and TPS60212 at TA = -40C to 85C, VI = 2.4 V and SNOOZE = VI (unless otherwise noted)
PARAMETER V(LBI) II(LBI) VO(LBO) LBI trip voltage LBI trip voltage hysteresis LBI input current TEST CONDITIONS VI = 1.6 V to 2.2 V, Tc = 0C to 70C For rising voltage at LBI V(LBI) = 1.3 V V(LBI) = 0 V, MIN 1.13 TYP 1.18 10 20 0.01 100 0.4 0.1 MAX 1.23 UNIT V mV nA V A
LBO output voltage low I(LBO) = 1 mA Ilkg(LBO) LBO leakage current V(LBI) = 1.3 V, V(LBO) = 3.3 V NOTE: During start-up of the converter the LBO output signal is invalid for the first 500 s.
electrical characteristics for power-good comparator of devices TPS60211 and TPS60213 at TA = -40C to 85C, VI = 2.4 V and SNOOZE = VI (unless otherwise noted)
PARAMETER V(PG) Vhys(PG) VO(PG) Ilkg(PG) Power-good trip voltage Power-good trip voltage hysteresis Power-good output voltage low TEST CONDITIONS Tc = 0C to 70C VO decreasing, Tc = 0C to 70C VO = 0 V, VO = 3.3 V, I(PG) = 1 mA 0.01 MIN 0.87 x VO TYP 0.91 x VO 1% 0.4 0.1 V A MAX 0.95 x VO UNIT V
Power-good leakage current V(PG) = 3.3 V NOTE: During start-up of the converter the PG output signal is invalid for the first 500 s.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
TYPICAL CHARACTERISTICS Table of Graphs
FIGURES IO VO IQ VO VO vs Output current (TPS60210 and TPS60212) Efficiency Output current Output voltage Quiescent supply current Output voltage Output voltage ripple Load transient response Line transient response NOTE: All typical characteristics were measured using the typical application circuit of Figure 21 (unless otherwise noted). TPS60210 TPS60212 vs Input voltage vs Input voltage vs Output current (TPS60210 and TPS60212) vs Input voltage (TPS60210 and TPS60212) vs Input voltage vs Output current in snooze mode vs Time (Exit from snooze mode) vs Time vs Time in snooze mode 3, 4 5 6 7, 8 9, 10 11 12 13 14, 15, 16 17, 18 19 20
EFFICIENCY vs OUTPUT CURRENT
100 90 80 70 Efficiency - % Efficiency - % 60 50 40 30 20 10 0 0.1 1 10 100 1000 VI = 2.7 V VI = 1.8 V VI = 2.4 V 100 90 80 70 60 50 40 30 20 10 0 0.1
EFFICIENCY vs OUTPUT CURRENT
VI = 1.8 V VI = 2.4 V VI = 2.7 V
1
10
100
IO - Output Current - mA
IO - Output Current - mA
Figure 3
Figure 4
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
TYPICAL CHARACTERISTICS
TPS60210
EFFICIENCY vs INPUT VOLTAGE
100 90 80 IO - Output Current - mA 70 Efficiency - % 60 50 IO = 50 mA 40 30 20 50 10 0 1.6 0 1.6 250 350 300
TPS60210 PEAK OUTPUT CURRENT vs INPUT VOLTAGE
200 150 100
2.0
2.4 2.8 VI - Input Voltage - V
3.2
3.6
2.0
2.4
2.8
3.2
3.6
VI - Input Voltage - V
Figure 5
TPS60210
Figure 6
TPS60212
OUTPUT VOLTAGE vs OUTPUT CURRENT
3.5 3.35
OUTPUT VOLTAGE vs OUTPUT CURRENT
VI = 2.7 V VI = 3.6 V
3.4 VI = 3.6 V 3.3 VO - Output Voltage - V VO - Output Voltage - V
3.30 3.25 VI = 1.8 V 3.20 3.15 3.10 3.05 3 1 10 100 1000 IO - Output Current - mA VI = 2.4 V
3.2
VI = 1.8 V VI = 2.7 V VI = 2.4 V
3.1
3.0
2.9
1
10 IO - Output Current - mA
100
Figure 7
Figure 8
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
TYPICAL CHARACTERISTICS
TPS60210 TPS60212
OUTPUT VOLTAGE vs INPUT VOLTAGE
3.4 3.3 VO - Output Voltage - V 3.2 50 mA 1 mA VO - Output Voltage - V 3.25 3.35 3.30
OUTPUT VOLTAGE vs INPUT VOLTAGE
1 mA
3.1 3.0
100 mA
3.20 50 mA 3.15
25 mA
2.9 2.8 2.7 1.6
3.10 3.05 3.00 1.6
2.0
3.2 2.4 2.8 VI - Input Voltage - V
3.6
2.0
2.4 2.8 VI - Input Voltage - V
3.2
3.6
Figure 9
QUIESCENT SUPPLY CURRENT vs INPUT VOLTAGE
40 38 I - Quiescent Current - A Q 36 34 32 30 28 26 24 22 20 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 VI - Input Voltage - V 10 0 0 0.2 0.4 IO = 0 mA SNOOZE = VI I - Quiescent Current - A Q 70
Figure 10
QUIESCENT SUPPLY CURRENT vs OUTPUT CURRENT IN SNOOZE MODE
VI = 2.4 V SNOOZE = GND
60 50
40 30 20
0.6 0.8
1
1.2 1.4
1.6
1.8
2
IO - Output Current - mA
Figure 11
Figure 12
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
TYPICAL CHARACTERISTICS
TPS60210 TPS60210
OUTPUT VOLTAGE vs TIME
VO - Output Voltage - V 3.6 3.5 3.4 3.3 3.2 VO- Output Voltage - V 3.38 3.36 3.34 3.32 3.30 3.28 3.26 3.24 3.22 0 50 100 150 200 250 300 350 400 450 500 t - Time - ms 0 5
OUTPUT VOLTAGE RIPPLE vs TIME
VI = 2.4 V IO = 1 mA
SNOOZE
High Low
10
15
20 25 30 t - Time - s
35
40
45
50
Figure 13
TPS60210
Figure 14
TPS60210
OUTPUT VOLTAGE RIPPLE vs TIME
3.38 3.36 3.34 VO- Output Voltage - V VO- Output Voltage - V 3.32 3.30 3.28 3.26 3.24 3.22 0 1 2 3 4 5 6 t - Time - s 7 8 9 10 VI = 2.4 V IO = 10 mA 3.38 3.36 3.34 3.32 3.30 3.28 3.26 3.24 3.22 0 1
OUTPUT VOLTAGE RIPPLE vs TIME
VI = 2.4 V IO = 100 mA
2
3
4 5 6 t - Time - s
7
8
9
10
Figure 15
Figure 16
12
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
TYPICAL CHARACTERISTICS
TPS60210 TPS60210
OUTPUT VOLTAGE RIPPLE IN SNOOZE MODE vs TIME
3.7 3.6 3.5 3.4 3.3 3.2 3.1 3 2.9 0 100 200 300 400 500 600 700 800 900 1000 t - Time - s VI = 2.4 V IO = 1 mA CO = 10 F (Tantalum) SNOOZE = Low VO - Output Voltage - V
OUTPUT VOLTAGE RIPPLE IN SNOOZE MODE vs TIME
3.7 3.6 3.5 3.4 3.3 3.2 3.1 3 2.9 0 100 200 300 400 500 600 700 800 900 1000 t - Time - s VI = 2.4 V IO = 1 mA CO = 2.2 F (Ceramic) SNOOZE = Low
VO - Output Voltage - V
Figure 17
Figure 18
TPS60210
TPS60210
LOAD TRANSIENT RESPONSE
VO - Output Voltage - V VI = 2.4 V 3.30 3.28 3.26 3.24 VI - Input Voltage - V VO - Output Voltage - V
LINE TRANSIENT RESPONSE
IO = 50 mA
3.32 3.30 3.28 3.26 2.8 V
I O- Output Current - mA
100 mA
10 mA 0 50 100 150 200 250 300 350 400 450 500 t - Time - s
2.2 V 0 1 2 3 4 5 6 t - Time - ms 7 8 9 10
Figure 19
Figure 20
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
APPLICATION INFORMATION capacitor selection
The TPS6021x devices require only four external capacitors to achieve a very low output voltage ripple. The capacitor values are closely linked to the required output current. Low ESR (< 0.1-) capacitors should be used at the input and output of the charge pump. In general, the transfer capacitors (C1 and C2) will be the smallest. A 1-F value is recommended if full load current performance is needed. With smaller capacitor values, the maximum possible load current is reduced and the linskip threshold is lowered. The input capacitor improves system efficiency by reducing the input impedance. It also stabilizes the input current of the power source. The input capacitor should be chosen according to the power supply used, the distance from the power source to the converter IC. CI is recommended to be about two to four times as large as the flying capacitors C1 and C2. The minimum required capacitance is 2.2 F. Larger values will improve the load transient performance and will reduce the maximum output ripple voltage. The larger the output capacitor, the better the output voltage accuracy, and the more output current can be drawn from the converter when programmed into snooze mode. Only ceramic capacitors are recommended for input, output and flying capacitors. Depending on the material used to manufacture them, ceramic capacitors might lose their capacitance over temperature and voltage. Ceramic capacitors of type X7R or X5R material will keep their capacitance over temperature and voltage, whereas Z5U- or Y5V-type capacitors will decrease in capacitance. Table 1 lists recommended capacitor values.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
APPLICATION INFORMATION
Table 2. Recommended Capacitor Values (Ceramic X5R and X7R)
LOAD CURRENT, ILOAD (mA) 0-100 0-100 0-100 0-100 0-50 0-25 0-10 FLYING CAPACITORS, C1/C2 (F) 1 1 1 2.2 0.47 0.22 0.1 INPUT CAPACITOR, CIN (F) 2.2 4.7 2.2 4.7 2.2 2.2 2.2 OUTPUT CAPACITOR, COUT (F) 2.2 4.7 10 4.7 2.2 2.2 2.2 OUTPUT VOLTAGE RIPPLE IN LINEAR MODE, VP-P (mV) 3 3 3 3 3 5 5 OUTPUT VOLTAGE RIPPLE IN SKIP MODE, VP-P (mV) 20 10 7 10 20 15 15
Table 3. Recommended Capacitor Types
MANUFACTURER Taiyo Yuden y PART NUMBER UMK212BJ104MG EMK212BJ224MG EMK212BJ474MG LMK212BJ105KG LMK212BJ225MG EMK316BJ225KL LMK316BJ475KL JMK316BJ106ML AVX 0805ZC105KAT2A 1206ZC225KAT2A SIZE 0805 0805 0805 0805 0805 1206 1206 1206 0805 1206 CAPACITANCE 0.1 F 0.22 F 0.47 F 1 F 2.2 F 2.2 F 4.7 F 10 F 1 F 2.2 F TYPE Ceramic Ceramic Ceramic Ceramic Ceramic Ceramic Ceramic Ceramic Ceramic Ceramic
Table 4. Recommended Capacitor Manufacturers
MANUFACTURER Taiyo Yuden AVX CAPACITOR TYPE X7R/X5R ceramic X7R/X5R ceramic INTERNET SITE http://www.t-yuden.com/ http://www.avxcorp.com/
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
APPLICATION INFORMATION typical operating circuit TPS60210
INPUT 1.6 V to 3.6 V Ci 2.2 F R1 R2 C1 1 F 7 1 4 TPS60210 5 IN OUT R3 LBI LBO C1+ C2+ 10 6 C2 1 F Low Battery Warning OUTPUT 3.3 V, 100 mA Co 2.2 F
3 8 C1- C2- 9 SNOOZE GND ON/OFF 2
Figure 21. Typical Operating Circuit TPS60210 With Low-Battery Comparator
INPUT 1.6 V to 3.6 V Ci 2.2 F R1 R2 C1 0.47 F
7 1 4 3 9
TPS60212 5 IN OUT R3 LBI LBO C1+ C1- SNOOZE GND 2 C2+ C2- 10 6 8 C2 0.47 F
OUTPUT 3.3 V, 50 mA Co 2.2 F Low Battery Warning
ON/OFF
Figure 22. Typical Operating Circuit TPS60212 With Low-Battery Comparator The current losses through the resistive divider used to set the low-battery threshold can be avoided if an additional MOSFET (like BSS138) is used in series to the resistors. This switch is controlled using the SNOOZE signal. When the SNOOZE-signal is taken high, the device is programmed into normal operating mode, the switch will turn on and the resistive divider draws current to set the LBI threshold voltage. When SNOOZE is taken low, the device is programmed into snooze mode during which the low-battery comparator is disabled. In addition, the resistive divider R1/R2 is disconnected from GND and therefore draws no current from the battery. A typical schematic for this circuit is shown in Figure 22.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
APPLICATION INFORMATION typical operating circuit TPS60211
INPUT 1.6 V to 3.6 V Ci 2.2 F PG 4 C1 1 F C1+ C2+ 7 TPS60211 5 IN OUT R1 10 6 C2 1 F Power-Good Signal OUTPUT 3.3 V, 100 mA Co 2.2 F
3 8 C1- C2- 9 SNOOZE GND ON/OFF 1,2
Figure 23. Typical Operating Circuit TPS60211 With Power-Good Comparator
power dissipation
The power dissipated in the TPS6021x devices depends mainly on input voltage (VI) and output current (IO) and is approximated by: P (DISS) +I O x 2xV * V for I tt I I O (Q) O (5)
By observing equation 5, it can be seen that the power dissipation is worse with a higher input voltage and a higher output current. For an input voltage of 3.6 V and an output current of 100 mA, the calculated power dissipation (P(DISS)) is 390 mW. This is also the point where the charge pump operates with its lowest efficiency. With the recommended maximum junction temperature of 125C and an assumed maximum ambient operating temperature of 85C, the maximum allowed thermal resistance junction to ambient of the system can be calculated. R QJA(max) + T J(MAX) * T A P DISS(max) + 125C * 85C + 102C W 390 mW (6)
PDISS must be less than that allowed by the package rating. The thermal resistance junction to ambient of the used 10-pin MSOP is 294C/W for an unsoldered package. The thermal resistance junction to ambient with the IC soldered to a printed circuit using a board layout as described in the application information section, the RJA is typically 200C/W, which is higher than the maximum value calculated previously. However, in a battery powered application, both the VI and the ambient temperature (TA) will typically be lower than the worst case ratings used in equation 6, and PDISS should not be a problem in most applications.
layout and board space
Careful board layout is necessary due to the high transient currents and switching frequency of the converter. All capacitors should be placed in close proximity to the device. A PCB layout proposal for a one-layer board is given in Figure 24. An evaluation module for the TPS60210 is available and can be ordered under product code TPS60210EVM-167. The EVM uses the layout shown in Figure 26. The EVM has the form factor of a 14-pin dual in-line package and can be mounted accordingly on a socket. All components, including the pins, are shown in Figure 24. The actual size of the EVM is 17,9 mm x 10,2 mm = 182,6 mm2.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
APPLICATION INFORMATION layout and board space (continued)
17,9 mm
C4
C1 R2 IC1 C5 R1 R3
10,2 mm
C3
R4 C2
Figure 24. Recommended Component Placement and Board Layout
Table 5. Component Identification
IC1 C1, C2 C3 C4 C5 R1, R2 R3 R4 TPS60210 Flying capacitors Input capacitor Output capacitor Stabilization capacitor for LBI Resistive divider for LBI Pullup resistor for LBO Pullup resistor for EN
Capacitor C5 should be included if large line transients are expected. This capacitor suppresses toggling of the LBO due to these line changes.
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
APPLICATION INFORMATION device family products
Other charge pump dc-dc converters from Texas Instruments are: Table 6. Product Identification
PART NUMBER TPS60100 TPS60101 TPS60110 TPS60111 TPS60120 TPS60121 TPS60122 TPS60123 TPS60130 TPS60131 TPS60132 TPS60133 TPS60140 TPS60141 TPS60200 TPS60201 TPS60202 TPS60203 LITERATURE NUMBER SLVS213 SLVS214 SLVS215 SLVS216 SLVS257 SLVS257 SLVS257 SLVS257 SLVS258 SLVS258 SLVS258 SLVS258 SLVS273 SLVS273 SLVS274 SLVS274 SLVS274 SLVS274 DESCRIPTION 2-cell to regulated 3.3-V, 200-mA low-noise charge pump 2-cell to regulated 3.3-V, 100-mA low-noise charge pump 3-cell to regulated 5.0-V, 300-mA low-noise charge pump 3-cell to regulated 5.0-V, 150-mA low-noise charge pump 2-cell to regulated 3.3-V, 200-mA high-efficiency charge pump with low-battery comparator 2-cell to regulated 3.3-V, 200-mA high-efficiency charge pump with power-good comparator 2-cell to regulated 3.3-V, 100-mA high-efficiency charge pump with low-battery comparator 2-cell to regulated 3.3-V, 100-mA high-efficiency charge pump with power-good comparator 3-cell to regulated 5.0-V, 300-mA high-efficiency charge pump with low-battery comparator 3-cell to regulated 5.0-V, 300-mA high-efficiency charge pump with power-good comparator 3-cell to regulated 5.0-V, 150-mA high-efficiency charge pump with low-battery comparator 3-cell to regulated 5.0-V, 150-mA high-efficiency charge pump with power-good comparator 2-cell to regulated 5.0-V, 100-mA charge pump voltage tripler with low-battery comparator 2-cell to regulated 5.0-V, 100-mA charge pump voltage tripler with power-good comparator 2-cell to regulated 3.3-V, 100-mA low-ripple charge pump with low-battery comparator 2-cell to regulated 3.3-V, 100-mA low-ripple charge pump with power-good comparator 2-cell to regulated 3.3-V, 50-mA low-ripple charge pump with low-battery comparator 2-cell to regulated 3.3-V, 50-mA low-ripple charge pump with power-good comparator
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TPS60210, TPS60211, TPS60212, TPS60213 REGULATED 3.3 V, LOW-RIPPLE CHARGE PUMP WITH ULTRALOW OPERATING CURRENT
SLVS296 - JUNE 2000
MECHANICAL DATA
DGS (S-PDSO-G10)
0,27 0,17 10 6
PLASTIC SMALL-OUTLINE PACKAGE
0,50
0,25 M
0,15 NOM 3,05 2,95 4,98 4,78
Gage Plane 0,25 1 3,05 2,95 5 0- 6 0,69 0,41
Seating Plane 1,07 MAX 0,15 0,05 0,10
4073272/A 03/98 NOTES: A. All linear dimensions are in millimeters. B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusion.
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IMPORTANT NOTICE Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue any product or service without notice, and advise customers to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those pertaining to warranty, patent infringement, and limitation of liability. TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with TI's standard warranty. Testing and other quality control techniques are utilized to the extent TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed, except those mandated by government requirements. Customers are responsible for their applications using TI components. In order to minimize risks associated with the customer's applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right of TI covering or relating to any combination, machine, or process in which such semiconductor products or services might be or are used. TI's publication of information regarding any third party's products or services does not constitute TI's approval, warranty or endorsement thereof.
Copyright (c) 2000, Texas Instruments Incorporated

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